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ORIGINAL RESEARCH article

Front. Signal Process., 25 March 2022
Sec. Radar Signal Processing
This article is part of the Research Topic Horizons in Signal Processing View all 6 articles

CRLBs for Location and Velocity Estimation for MIMO Radars in CES-Distributed Clutter

  • Department of Information Engineering, University of Pisa, Pisa, Italy

In this article, we investigate the problem of jointly estimating target location and velocity for widely separated multiple-input multiple-output (MIMO) radar operating in correlated non-Gaussian clutter, modeled by a complex elliptically symmetric (CES) distribution. More specifically, we derive the Cramér–Rao lower bounds (CRLBs) when the target is modeled by the Swerling 0 model and the clutter is complex t-distributed. We thoroughly analyze the impact of the clutter correlation and spikiness to provide accurate performance estimation. Index terms—Cramér–Rao lower bounds (CRLBs), MIMO radar, location and velocity estimation, performance analysis, complex elliptically symmetric (CES) distributed, and complex t-distribution.

1 Introduction

Multiple-input multiple-output (MIMO) radars have attracted increasing attention in recent years, as proved by the many published articles (see, for instance, Fishler et al., 2004; Li and Stoica, 2008; Davis, 2015). MIMO radars can be classified as coherent or noncoherent (He et al., 2010a; Derham et al., 2010), and colocated (Li and Stoica, 2007) or widely distributed (Haimovich et al., 2007).

Estimating target parameters in MIMO radars is one of the far-reaching research topics; hence, various research studies have considered different scenarios, with different antenna deployment (Fishler et al., 2006; Li and Stoica, 2009), target models (in motion or static target) (Hassanien et al., 2012), and various estimation algorithms (Stoica and Nehorai, 1990; Tajer et al., 2010; Min et al., 2011). The Cramér–Rao lower bound (CRLB) is a well-known tool for evaluating target parameter estimation performance in clutter. In Godrich et al., (2008a), Godrich et al., (2010), the CRLBs were derived for target localization in noncoherent and coherent MIMO radars. The CRLB for target velocity was presented in He et al., (2010b), while the CRLB for joint estimation of target location and velocity in case of noncoherent MIMO radars was derived in He et al., (2010a). In Godrich et al., (2008b), He et al., (2008), CRLBs were derived for MIMO radars with widely separated antennas.

In all the cited articles, the clutter is modeled as a Gaussian stochastic process, white or colored. Such assumption is a good approximation in many cases, but not always, particularly when the clutter is very spiky, for e.g., in high resolution radars (Brekke et al., 2010). In MIMO radars, sometime the clutter has been modeled as a non-Gaussian process by the compound-Gaussian (CG) (Farina et al., 1997; Gini, 1998; Gini and Greco, 1999; Sangston et al., 1999; Sangston et al., 2012) or the complex elliptically symmetric (CES) distributions (Ollila et al., 2012; Fortunati et al., 2019) that include a wide variety of distributions such as complex normal (CN) (Goodman, 1963), complex generalized Gaussian (Novey et al., 2009), complex-t (Ct), complex-k, and all the other CG distributions (Krishnaiah and Lin, 1986; Zhang et al., 2014; Zhang et al., 2017).

The novel contribution of this article is to derive the CRLBs on the estimation of location and velocity under the assumption that the non-Gaussian correlated clutter is modeled by a Ct-distribution. We then analyze the impact of the clutter correlation and spikiness on the estimation performance.

This article is organized as follows: the data model is described in Section 2. In Section 3, the general CES model and the complex t-distribution are summarized. In Section 4, we derive the analytical expression of the CRLBs for the estimation of target location and velocity, and some numerical results are reported in Section 5 to investigate the theoretical findings.

2 Data Model

Consider a coherent MIMO radar with M transmit (TX) and N receive (RX) antennas, widely dispersed in a 2-D plane as shown in Figure 1. In order to simplify the CRLB derivation of target location and velocity, we assume an isotropic target whose unknown complex amplitude is ζ = ζR + I. The unknown target location is (x, y), and the unknown target velocity is (vx, vy). The known locations of the M transmitters are (xkt,ykt),(k=1,,M) and of the N receivers are (xlr,ylr),(l=1,,N). ϕk is the orientation of the kth transmitter, and φl is the orientation of the lth receiver with respect to the xaxis.

FIGURE 1
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FIGURE 1. Transmitters and receivers location with respect to the moving target.

The echo at the lth receiver from the transmission of all the M transmitters and reflected from the target, after down-conversion and sampling, is

rln=EMζk=1Mej2πf0τlkej2πflknTssknTsτlk+zln,l=1,,Nn=1,.,Ns,(1)

where ζ is the target complex reflectivity (unknown and deterministic), f0 is the carrier frequency (carrier frequencies of all transmitters are assumed to be identical), Ts is the sampling time (chosen to satisfy the Nyquist criterion), and Ns is the number of samples in the observation period, sk(Δn)=f(Δn)rect(ΔnTp) with Δn = (nTsτlk), which is the complex baseband signal received by the lth receiver sent by the kth transmitter. The rect(ΔnTp) models the single pulse time interval, while f(Δn) refers to the specific class of signal implementation, and Tp refers to the pulse duration. Each signal is emitted by an individual transmitter antenna with energy Es, while E = EsM is the total transmitted energy. Finally, zl[n] is the clutter echo at the lth receiver.

τlk represents the time delay of a signal given by

τlk=dkt+dlrc,(2)

where dkt=(xktx)2+(ykty)2 is the path from the kth TX antenna to the target, dlr=(xlrx)2+(ylry)2 is the path from the target to the lth RX antenna, and c indicates the speed of light.

flk is the target Doppler frequency shift given by

flk=vxxktx+vyyktyλdkt+vxxlrx+vyylryλdlr,(3)

where λ indicates the wavelength of the carrier frequency.

In our derivation, we assume that the transmitted signals are orthogonal (Peilin Sun et al., 2014). Furthermore, they retain approximately orthogonality, even after a variety of allowed time delays and Doppler frequency shifts, that is,

n=1NssknTsτlksk*nTsτlkej2πflkflknTs1ł=l,k=k0łl,kkτlk,flk,τlk,flk.(4)

The orthogonality as given in Eq. 4 is clearly a strong condition if applied to all possible delays and Doppler frequencies. Despite this, for reasonable values of Doppler frequencies and the set of target and radar parameters of this work, we verified that the cross-ambiguity functions are negligible compared to the auto-ambiguity functions; thus, the orthogonal condition can be considered approximately met.

Finally, the Ns-dimensional observation vector at the lth receiver can be expressed as rl=rl[1]rl[2]rl[Ns]T.

3 Complex Elliptically Symmetric Distribution

Complex elliptically symmetric (CES) distributions are commonly used to model non-Gaussian heavy-tailed radar clutter (Zhang et al., 2014; Fortunati et al., 2018; Fortunati et al., 2019; Raninen et al., 2021). The m-variate random vector (r.v) zCm that follows the CES model has a probability density function (pdf) of the form,

fzz=Cm,gΣ1gzμHΣ1zμ,(5)

where μCm and the m × m matrix Σ denote the symmetry center and scatter matrix, respectively. The function g: R0+R+, called density generator function, satisfies the constraint δm,g0tm1g(t)dt<, and (.)H refers to the Hermitian (complex conjugate and transpose) operator. Cm,g is a normalizing coefficient such that fz(z) integrates to 1 and Cm,g=2(Smδm,g)1, where Sm2πmΓ(m).

Then, the clutter can be represented in short notation by

zCEmμ,Σ,g=CEm,gμ,Σ.(6)

3.1 t-Distributed Clutter

A particular case of CES-distributions is the Ct-distribution (Krishnaiah and Lin, 1986; Ollila et al., 2012), in short notation zCtm,ν(μ, Σ).

For a complex t-distribution of dimension m, the generating function is given by

gt=1+2tν2m+ν2(7)

and Cm,g=2mΓ(2m+ν2)(πν)mΓ(ν2) is the normalizing constant. ν is the shape parameter of the distribution, and it is related to the spikiness of the clutter. The lower the value of ν, the spikier is the clutter (Sangston et al., 2012). For ν, the t-distribution degenerates into the Gaussian one.

Here, we investigate two different scenarios for the clutter. Model I: the clutter samples are uncorrelated in space and time. Model II: the clutter samples are temporally uncorrelated but spatially correlated. The mean value is 0, that is, μ = 0.

4 The Joint Cramér–Rao Lower Bound

The CRLB provides a lower bound of the variance of any unbiased estimator of unknown deterministic parameters. Given ψ = [x, y, vx, vy, ζR, ζI] as the vector of all the unknown parameters in the received signal, we derive the CRLBs for the MIMO radar. Since we assume here that the target has already been detected and we want to estimate target range and velocity, we consider the target reflectivity, ζR and ζI, as nuisance parameters (Gini and Reggiannini, 2000; Fortunati et al., 2010), then we derive the CRLBs of the unknown vector βp×1 = [x, y, vx, vy], p = 4.

4.1 CRLB for Target Range and Velocity

In order to derive the CRLB of target location and velocity, the first step is to calculate the Fisher information matrix (FIM) and then to invert it, CRLB(ψ) = [J(ψ)]−1.

The FIM matrix is defined as

Jψi,j=Er,ψψiψjlnpr;ψ,(8)

where E{.} indicates the expectation operator, ln p(r; ψ) is the log-likelihood (LL) function, and r is the data vector. The FIM is a p × p symmetric positive semi-definite matrix after deleting the rows and columns of the nuisance parameter.

Since (1) is a function of time delay and Doppler frequency shift, we introduce the (2 + NM)-dimensional parameter vector Θ=[τ11,τ12,,τlk,f11,f12,,flk,ζR,ζI]T, and since ψ is a function of Θ, in order to compute the FIM, the chain rule (He et al., 2010a) is applied; therefore, the FIM can be expressed as

Jψ=PJΘPT,(9)

where P=ΘTψ depends on the geometry of the scenario and is given by

P=ΘTψ=U4×2NM04×202×4I2,(10)

where 0 and I are the zero and identity matrices, respectively, while U is given by

U=τ11xτNMxf11xfNMxτ11yτNMyf11yfNMy00f11vxfNMvx00f11vyfNMvy.(11)

The details on the derivation of the elements of U are in He et al. (2010a). J(Θ) is the Jacobian matrix such that

JΘi,j=Er,ΘΘiΘjlnpr;Θ.(12)

Matrix J(Θ), computed as in Eq. 12, can be divided into four submatrices as follows:

JΘ=D2NM×2NMG2NM×2G2×2NMTL2×2,(13)

where D=DτDτfDfτDf in which Dτ, Df, and DτfRNM×NM. The lower right submatrix L involves the derivatives of the target complex scattering coefficient, L=LζR00LζI. Finally, the upper right submatrix involves the derivatives related to all parameters, time delay, the Doppler frequency, and the target complex reflectivities, then G=GτζRGfζRGτζIGfζI.

By exploiting the chain rule for Eq. 9, the FIM of ψ is given by

Jψ=UDUTUGGTUTL.(14)

Eventually, since our aim is to calculate the CRLBs of the vector β, we get it as (He et al., 2008)

CRLBβ=UDGL1GTUT1,(15)

where the diagonal elements of the CRLB matrix represent the lower bound of the variances of the parameters of interest.

1) CRLB for Clutter Model I: If the clutter is independent in both the time and space domains, then the clutter samples zl[n] (l = 1, … , N n = 1, … , Ns) are IID.

In this case, the log-likelihood function is given by

lnpr|Θ=lnn=1NSl=1Nprln|Θ=C+n=1Nsl=1Nlnprln|Θ=C+n=1Nsl=1Nlngtln,(16)

where C is a generic constant that does not depend on the parameters of interest, and the pdf of each sample rl[n] is given by

prln;Θ=C1,gσ2gtln,(17)

where C1,g=2Γ(2+νν)(πν)Γ(ν2), tl[n] is the quadratic form tl[n]=1σ2rl[n]EMζul[n]2, ul[n]k=1Mϒlk[n]sk[Δn], and ϒlk[n]=ej2πf0τlkej2πflknTs represents each element of the ϒ[n] matrix of all transmitter and receiver antennas.

Each element of the Jacobian matrix is

JΘi,j=E2lnpr|ΘΘiΘj=En=1Nsl=1Ngtlngtlngtln2gtln2tlnΘitlnΘj+gtlngtln2tlnΘiΘji,j=1,,2NM+2(18)

yielding g(tl[n])g(tl[n])=2N+νν1+2tl[n]ν1, and g(tl[n])g(tl[n])g(tl[n])2g(tl[n])2=22N+νν21+2tl[n]ν2, where the first derivative of g is g(tl[n])=g[tl]tltl[n]Θ.

Note that, in computing the derivatives of the LL function with respect to the parameters in Eq. 18, we consider the orthogonality conditions in Eq. 4, and then the generic element of Eq. 18 is calculated with the derivative expressions as follows:

tpnflk=4πnTsσ2EMIζϒlknskΔnrp*n4πnTsσ2EM|ζ|2IϒlknskΔnup*nδlp;(19)
2tpnflkflk=8π2n2Ts2σEMRζϒlknskΔnrp*nEMζ*up*n+8π2n2Ts2σEM|ζ|2Rej2πf0τlkτlkej2πflkflknTsskΔnsk*Δnδlp,ll,kk,(20)

where the aforementioned equations represent the first and second derivatives with respect to (w.r.t.) the Doppler frequency. The derivatives w.r.t. time delay and target complex reflectivity are as follows:

tpnτlk=4πf0σ2EMIζrp*nϒlknskΔn2σ2EMRζrp*nϒlknskΔn+4πf0σ2EM|ζ|2Iup*nϒlknskΔn+2σ2EM|ζ|2Iup*nϒlknskΔnδlp;(21)
2tpnτlkτlk=2σEMRζrp*nϒlkn4π2f02skΔnj4πf0skΔn+skΔn+2σEM|ζ|2Rϒlknup*n4π2f02skΔnj4πf0skΔn+skΔn+ej2πf0τlkτlkej2πflkflknTsj2πf0skΔn+skΔnj2πf0skΔn+skΔn)δlp,ll,kk;(22)
tpnζR=2σ2EMRupnrp*n+2σ2EMζRupn2;(23)
tpnζI=2σ2EMIupnrp*n+2σ2EMζIupn2;(24)
2tpnζRζR=2tpnζIζI=2σEMupn2,2tpnζRζI=0.(25)

The second cross-derivatives w.r.t. Doppler frequency, time delay, and target complex reflectivity are

2tpnflkζR=4πnTsσEMIϒlknskΔnrp*n8πnTsσEMζRIϒlknskΔnup*nδlp;(26)
2tpnflkζI=4πnTsσEMRϒlknskΔnrp*n8πnTsσEMζIIϒlknskΔnup*nδlp;(27)
2tpnτlkζR=2σEMRrp*nϒlknj2πf0skΔn+skΔn+4σEMζRRup*nϒlknj2πf0skΔn+skΔnδlp;(28)
2tpnτlkζI=2σEMRjrp*nϒlknj2πf0skΔn+skΔn+4σEMζIRup*nϒlknj2πf0skΔn+skΔnδlp;(29)
2tpnflkτlk=4πnTsσEMIζrp*nϒlknj2πf0skΔn+skΔn4πnTsσEM|ζ|2Iup*nϒlknj2πf0skΔn+skΔn+ej2πf0τlkτlkej2πflkflknTsskΔnj2πf0sk*Δn+sk*Δnδlp,ll,kk.(30)

Note that δ(lp) = 1 for l = p and 0 elsewhere, and sk(Δn)=sk(Δn)τlk. More details about the derivations are presented in the Supplementary Appendix under Clutter Model I.

2) CRLB for Clutter Model II: In this case, the clutter is correlated in the space domain and independent in the time domain, meaning that the Ns clutter vectors z[n]=z1[n],z2[n],,zN[n]T(n=1,,Ns) are IID, then the scatter matrix Σ is a N × N semi-definite positive matrix. Under this condition, the observed N-dimensional signal vector can be written as

rn=EMζϒnsΔn+zn,n=1,.,Ns,(31)

where the s[Δn]=s1(Δn),s2(Δn),,sM(Δn)T.

The pdf of the observation vector is given by

prn;Θ=CN,g|Σ|gtn,(32)

where CN,g=2NΓ(2N+νν)(πν)NΓ(ν2), and the quadratic form is given by

tn=p=1Nq=1Nηp,qrp*nrqn2EMRζp=1Nq=1Nηp,qrp*nuqn+EM|ζ|2p=1Nq=1Nηp,qup*nuqn,(33)

where ηp,q is the inverse of scatter matrix, ηpq=ΔΣ1p,q.

Subsequently, the log-likelihood function is given by

lnpr|Θ=lnn=1NSprn|Θ=C+n=1Nslnprn|Θ=C+n=1Nslngtn,(34)

where C is a generic constant, and each element of the Jacobian matrix is

JΘi,j=E2lnpr|ΘΘiΘj=;
En=1Nsgtngtngtn2gtn2tnΘitnΘj+gtngtn2tnΘiΘj;(35)
i,j=1,,2NM+2.

Afterward, the generic element of Eq. 35 is derived using the derivative expressions as follows

tnflk=4πnTsEMIζϒlknskΔnp=1Nηplrp*n;
4πnTsEM|ζ|2IϒlknskΔnp=1Nηplup*nδlp;(36)
2tnflkflk=8π2n2Ts2EMRζϒlknskΔnp=1Nηplrp*n;
8π2n2Ts2EM|ζ|2RϒlknskΔnp=1Nηplup*n;
8π2n2Ts2EM|ζ|2RηllϒlknϒlknskΔnsk*Δn;
δlp,ll,kk.

The aforementioned equations represent the first and second derivatives w.r.t. Doppler frequency. Next, the derivatives w.r.t. time delay are given as follows:

tnτlk=4πf0EMIζϒlknskΔnp=1Nηplrp*n;
2EMRζϒlknskΔnp=1Nηplrp*n;
+4πf0EM|ζ|2IϒlknskΔnp=1Nηplup*n;
+2EM|ζ|2RϒlknskΔnp=1Nηplup*nδlp;
2tnτlkτlk=8π2f02EMRζϒlknskΔnp=1Nηplrp*n;
8πf0EMIζϒlknskΔnp=1Nηplrp*n;
2EMRζϒlknskΔnp=1Nηplrp*n;
8π2f02EM|ζ|2RϒlknskΔnp=1Nηplup*n;
+8πf0EM|ζ|2IϒlknskΔnp=1Nηplup*n;
+2EM|ζ|2RζϒlknskΔnp=1Nηplrp*n;
8π2f02EM|ζ|2RηllϒlknϒlknskΔnsk*Δn;
4πf0EM|ζ|2IηllϒlknϒlknskΔnsk*Δn;
4πf0EM|ζ|2IηllϒlknϒlknskΔnsk*Δn;
+2EM|ζ|2RηllϒlknϒlknskΔnsk*Δn;
δlp,ll,kk.

Furthermore, the derivatives w.r.t. target complex reflectivity are as follows:

tnζR=2EMRp=1Nq=1Nηpqrp*nuqn+2EMζRp=1Nq=1Nηpqup*nuqn;(40)
tnζI=2EMIp=1Nq=1Nηpqrp*nuqn+2EMζIp=1Nq=1Nηpqup*nuqn;(41)
2tnζRζR=2tnζIζI=2σEMp=1Nq=1Nηpqup*nuqn,2tnζRζI=0.(42)

Also, these are the cross-derivatives of unknown parameters, for the clutter model II.

2tnflkζR=4πnTsEMIϒlknskΔnp=1Nηplrp*n8πnTsEMζRIϒlknskΔnp=1Nηplup*nδlp;(43)
2tnflkζI=4πnTsEMRϒlknskΔnp=1Nηplrp*n8πnTsEMζIRϒlknskΔnp=1Nηplup*nδlp;(44)
2tnτlkζR=4πf0EMIϒlknskΔnp=1Nηplrp*n2EMRϒlknskΔnp=1Nηplrp*n+4EMζRRϒlknskΔnp=1Nηplup*n+8πf0EMζRIϒlknskΔnp=1Nηplup*n)δlp;(45)
2tnτlkζI=4πf0EMRϒlknskΔnp=1Nηplrp*n+2EMIϒlknskΔnp=1Nηplrp*n+4EMζIRϒlknskΔnp=1Nηplup*n+8πf0EMζIIϒlknskΔnp=1Nηplup*n)δlp;(46)
2tnflkτlk=8π2f0nTsEMRζϒlknskΔnp=1Nηplrp*n+4πnTsEMIζϒlknskΔnp=1Nηplrp*n8π2f0nTsEM|ζ|2RζϒlknskΔnp=1Nηplup*n4πnTsEM|ζ|2IζϒlknskΔnp=1Nηplup*n8π2f0nTsEM|ζ|2RηllϒlknϒlknskΔnsk*Δn+4πnTsEM|ζ|2IηllϒlknϒlknskΔnsk*Δn)δlp,ll,kk.(47)

The details about derivations are reported in the Supplementary Appendix under Clutter Model II.

5 Numerical Analysis

In the following, we investigate the estimation for the circular MIMO radar shown in Figure 2. A M × N = 4 × 4 MIMO radar is considered whose antenna orientations are ϕ1t=φ1r=0,ϕ2t=φ2r=90,ϕ3t=φ3r=180,ϕ4t=φ4r=270 with dkt=dlr=500m. An isotropic target (T) with a complex scattering coefficient ζ=1+1j2 is placed at x = y = 0 m with velocity vx=vy=50ms.

FIGURE 2
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FIGURE 2. Antenna placement.

Moreover, the carrier frequency is f0 = 10 GHz, the sampling frequency is fS = 9 MHz, the pulse duration is Tp = 0.56 ms, and the observation time is Tobs = 2.2 ms. The received waveforms are s(nTsτlk)=ej2πΔfk(nTsτlk) with frequency increment Δf = 1 MHz between sk[n] and sk+1[n] to satisfy the orthogonality assumption and with each waveform energy Es = 1. The signal-to-clutter ratio (SCR) is defined as:

SCR=k=1Msk2EzlHzl.(48)

The clutter samples are IID and t-distributed, then EzlHzl=Nsνν2σ2, where E|zl|2=νν2σ2 is the variance of a complex-t clutter. From the last equation, it is evident that to guarantee a finite positive power, ν > 2.

Following this, we chose the spikier clutter case ν = 2.1. Figures 3 and 4 show the range and Doppler frequency CRLBs of the spikier clutter case for both models I and II, respectively. In addition, we set σ2 = 1, and the CRLBs in Figure 4 are shown for spatially correlated clutter.

FIGURE 3
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FIGURE 3. CRLB for target location and velocity estimation in Clutter Model I.

FIGURE 4
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FIGURE 4. CRLB for target location and velocity estimation in Clutter Model II.

Considering (Zhang et al., 2014) the spatially correlated clutter is such that

Σp,q=σ2ρ|pqΔαp,q|,(49)

where ρ is a constant value and we chose ρ = 0.9, and Δαp,q is the angular distance from the pth receiver to clutter cell and from clutter to the qth receiver.

In the following figures, the joint CRLBs of target location and velocity for different values ν are presented for both clutter cases. We only show CRLBx and CRLBvx, since we set the same numerical values for x and y as well as for vx and vy; therefore, the CRLBs along the two directions, in this case, are the same.

According to Figure 5, a larger value of ν leads to an increase of the CRLBs in clutter case I. It is worth noting that the clutter power depends on both the scale parameter σ2 and the shape parameter ν. In these figures, σ2 = 1, then to keep constant the SCR for different values of ν, the energy of the transmitted signals is changed accordingly.

FIGURE 5
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FIGURE 5. CRLBs vs. SCR with different ν, Clutter Model I.

In Figure 6, we plot the CRLBs for the correlated clutter (Model II). In this case, the CRLB tends to increase for lower ν. It is apparent, anyway, that the differences in both models I and II are small with varying values of ν, at least in the tested configuration.

FIGURE 6
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FIGURE 6. CRLBs vs. SCR with different ν, Clutter Model II, ρ = 0.9.

To get a better look at the impact of the parameter ν on the target parameter estimation, under both Model I and Model II, Table 1 provides the CRLBs corresponding to x and vx at SCR = 0 dB with different values of ν. CRLBs of y and vy behave quite similarly.

TABLE 1
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TABLE 1. CRLBs of x and vx in clutter Model I and Model II with different values of ν, SCR = 0 dB, and ρ = 0.9.

Next, in order to investigate the effect of the correlation coefficient ρ in clutter Model II, Figures 79 show the CRLBs as a function of ρ for ν = 2.1 and SCR = 0 dB when the target is still, moving with vx=10ms, vy=35ms, and with vx=vy=50ms, respectively. When the target is still, the CRLBs decrease with increasing values of ρ from −1 to 1, (but ρ has a large impact only when its values are in the interval [0.8; 1]). When the target is moving, the behavior of the CRLBs depends on the value of the target velocity. For some combination of velocity and correlation values, the CRLBs show peaks and notches but the minimum is again reached for ρ = 1. In addition, Figure 10 presents the CRLBs as a function of ρ for ν = 2.1, SCR = 0 dB, and vx=vy=50ms when the transmitter/receiver antennas are rotated clockwise of 45° with respect to (w.r.t.) the configuration of the previous figures. The CRLBs on the target velocities do not depend strongly on the angular position but the CRLBs on the positions, conversely, do. To better analyze this dependency, keeping fixed the target velocity, (modulus and direction) we rotated counterclockwise the 4 RX/TXs, and in Figures 1114 we show the CRLBs as a function of the angle between the velocity and the TX/RX on the right (in Figure 2, this angle is equal to −45°), for three values of the correlation coefficient, in the range [−45°: 45°]. Due to the symmetry of the MIMO configuration, these CRLBs are periodic of 90°. These results confirm that for some values of ρ the CRLBs of the target positions strongly depend on the velocity angular direction.

FIGURE 7
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FIGURE 7. CRLBs vs. ρ, Clutter Model II with ν = 2.1, SCR = 0 dB, and vx = vy = 0 m/s.

FIGURE 8
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FIGURE 8. CRLBs vs. ρ, Clutter Model II with ν = 2.1, SCR = 0 dB, and vx = 10, vy = 35 m/s.

FIGURE 9
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FIGURE 9. CRLBs vs. ρ f, Clutter Model II with ν = 2.1, SCR = 0 dB, and vx = vy = 50 m/s.

FIGURE 10
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FIGURE 10. CRLBs vs. ρ, Clutter Model II for 45° shifted TX/RX antennas with ν = 2.1, SCR = 0 dB, and vx = vy = 50 m/s.

FIGURE 11
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FIGURE 11. CRLBx vs. ϕk1 antenna position, Clutter Model II for different ρ with ν = 2.1, SCR = 0 dB, and vx = vy = 50 m/s.

FIGURE 12
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FIGURE 12. CRLBy vs. ϕk1 antenna position, Clutter Model II for different ρ with ν = 2.1, SCR = 0 dB, and vx = vy = 50 m/s.

FIGURE 13
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FIGURE 13. CRLBvx vs. ϕk1 antenna position, Clutter Model II for different ρ with ν = 2.1, SCR = 0 dB, and vx = vy = 50 m/s.

FIGURE 14
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FIGURE 14. CRLBvy vs. ϕk1 antenna position, Clutter Model II for different ρ with ν = 2.1, SCR = 0 dB, and vx = vy = 50 m/s.

In Figures 15 and 16, the relation between the bounds and the number of antennas is shown, when the target is located in (0,0). These figures show the effect of increasing the number of sensors in two different scenarios: 1) the radius of the circle is constant, r=dlr=dkt=500m, and the TX/RX antennas are uniformly distributed on the circumference, and 2) the linear distance between each TX/RX antenna pair is fixed to dm = 49.06 m, and the radius of the circle is variable as a function of the number of antennas M, r=dm2sin(πM). As shown in these figures, the performance of the joint target parameter estimation can be remarkably improved by increasing the number of antennas, and this is particularly evident in the second scenario and for the velocity.

FIGURE 15
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FIGURE 15. CRLBx vs. number of antenna, Clutter Model I with ν = 2.1, SCR = 0 dB, and vx = vy = 50 m/s.

FIGURE 16
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FIGURE 16. CRLBvx vs. number of antenna, Clutter Model I with ν = 2.1, SCR = 0 dB, and vx = vy = 50 m/s.

Additionally, to assess the maximum achievable accuracy of the considered MIMO radar over the area of interest, we define the errors (Maddio et al., 2015; Passafiume et al., 2017; Cidronali et al., 2020) as

errxy=CRLBx+CRLByerrvxvy=CRLBvx+CRLBvy.(50)

Figures 17 and 18 illustrate the maximum achievable accuracy (or the error pattern over the area) attained by Eq. 50, in terms of CRLBs in both the clutter models I and II for varying positions with vx = vy = 50 m/s, while Figures 19 and 20 show the maximum achievable accuracy for a fixed target. These figures are all calculated for SCR = −15 dB and ν = 2.1.

FIGURE 17
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FIGURE 17. Maximum achievable accuracy when the target is moving, Clutter Model I, ν = 2.1 and SCR = −15 dB.

FIGURE 18
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FIGURE 18. Maximum achievable accuracy when the target is moving, Clutter Model II, ρ = 0.9, ν = 2.1, and SCR = −15 dB.

FIGURE 19
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FIGURE 19. Maximum achievable accuracy when the target is still, Clutter Model I, ν = 2.1 and SCR = −15 dB.

FIGURE 20
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FIGURE 20. Maximum achievable accuracy when the target is still, Clutter Model II, ρ = 0.9, ν = 2.1, and SCR = −15 dB.

Depending on the value of the target velocity along the x and y directions and on the clutter correlation, the shape of the error functioning inside the circle is different, but the range of variations in the considered area is always small, for both range and velocity, for both clutter models I and II.

To check the changes in the CRLBs as a function of the correlation coefficient ρ, in Figure 21, the maximum achievable accuracy is shown for the same scenario described in Figure 18 but for ρ = 0. It is worth observing that ρ = 0 does not mean that the clutter components are independent but only uncorrelated because they are not Gaussian-distributed.

FIGURE 21
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FIGURE 21. Maximum achievable accuracy when the target is moving, Clutter Model II, ρ = 0, ν = 2.1, and SCR = −15 dB.

Finally, to investigate the impact of the position of the transmitters and receivers on the performance of the radar, the error function is shown for a different configuration in Figures 22 and 23, where the receiver antennas are shifted of 45° with respect to the receiver; transmitters and receivers are represented by black and red triangles, respectively. As evident in Figures 22 and 23, configurations with shifted receiver antennas are similar to those of colocated antennas in Figures 17 and 18. The CRLBs are much more affected by the presence of the clutter correlation.

FIGURE 22
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FIGURE 22. Maximum achievable accuracy for shifted receiver antennas when the target is moving, Clutter Model I, ν = 2.1 and SCR = −15 dB.

FIGURE 23
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FIGURE 23. Maximum achievable accuracy for shifted receiver antennas when the target is moving, Clutter Model II, ρ = 0, ν = 2.1, and SCR = −15 dB.

6 Conclusion

This article presents the derivation of the CRLBs for the estimation of position and velocity of an isotropic target in a coherent MIMO radar with orthogonally transmitted waveforms in the presence of correlated non-Gaussian clutter, modeled by the complex t-distribution. We derived the CRLBs for two different scenarios: 1) the clutter samples are independent in space and time and 2) the clutter samples are temporally independent but spatially correlated. We then investigated the estimation accuracy as a function of the SCR, the clutter spikiness, and the clutter spatial correlation as well as maximum achievable accuracy in parameter estimation for several radar configurations. The CRLBs show a weak dependency on the spikiness of the clutter but, conversely, a strong dependency on the angular correlation, particularly for the moving target.

Author Disclaimer

The views and conclusions contained are those of the authors and should not be interpreted as necessarily representing the official policies or endorsements, either expressed or implied, of the Air Force Office of Scientific Research or the United States government.

Data Availability Statement

The raw data supporting the conclusion of this article will be made available by the authors, without undue reservation.

Author Contributions

All authors listed have made a substantial, direct, and intellectual contribution to the work and approved it for publication.

Funding

The work of MG and FG has been partially supported by the Italian Ministry of Education and Research (MIUR) in the framework of the CrossLab Project (Departments of Excellence) of the University of Pisa, Laboratory of Industrial Internet of Things (IIoT). This work has been partially funded also by EOARD/AFRL grant FA9550-17-1-0344 on “Exploiting Spatial Diversity in MIMO and Massive MIMO Radar Systems.”

Conflict of Interest

The authors declare that the research was conducted in the absence of any commercial or financial relationships that could be construed as a potential conflict of interest.

Publisher’s Note

All claims expressed in this article are solely those of the authors and do not necessarily represent those of their affiliated organizations, or those of the publisher, the editors, and the reviewers. Any product that may be evaluated in this article, or claim that may be made by its manufacturer, is not guaranteed or endorsed by the publisher.

Supplementary Material

The Supplementary Material for this article can be found online at: https://www.frontiersin.org/articles/10.3389/frsip.2022.822285/full#supplementary-material

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Keywords: Cramér–Rao lower bounds (CRLBs), MIMO radar, location and velocity estimation, performance analysis, complex elliptically symmetric (CES) distributed, complex t-distribution

Citation: Rojhani N, Greco MS and Gini F (2022) CRLBs for Location and Velocity Estimation for MIMO Radars in CES-Distributed Clutter. Front. Sig. Proc. 2:822285. doi: 10.3389/frsip.2022.822285

Received: 25 November 2021; Accepted: 28 January 2022;
Published: 25 March 2022.

Edited by:

Vishal Monga, The Pennsylvania State University (PSU), United States

Reviewed by:

Bosung Kang, University of Dayton Research Institute (UDRI), United States
Omar Aldayel, King Saud University, Saudi Arabia

Copyright © 2022 Rojhani, Greco and Gini. This is an open-access article distributed under the terms of the Creative Commons Attribution License (CC BY). The use, distribution or reproduction in other forums is permitted, provided the original author(s) and the copyright owner(s) are credited and that the original publication in this journal is cited, in accordance with accepted academic practice. No use, distribution or reproduction is permitted which does not comply with these terms.

*Correspondence: Neda Rojhani, bmVkYS5yb2poYW5pQGRpaS51bmlwaS5pdA==

Disclaimer: All claims expressed in this article are solely those of the authors and do not necessarily represent those of their affiliated organizations, or those of the publisher, the editors and the reviewers. Any product that may be evaluated in this article or claim that may be made by its manufacturer is not guaranteed or endorsed by the publisher.